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2008 IEEE INTERNATIONAL RF AND MICROWAVE CONFERENCE PROCEEDINGS 2008 IEEE INTERNATIONAL RF AND MICROWAVE CONFERENCE PROCEEDINGS 2008 IEEE INTERNATIONAL RF AND MICROWAVE CONFERENCE PROCEEDINGS 2008 IEEE INTERNATIONAL RF AND MICROWAVE CONFERENCE PROCEEDINGS December 2December 2December 2December 2----4, 2008, Kuala Lumpur, MALAYSIA4, 2008, Kuala Lumpur, MALAYSIA4, 2008, Kuala Lumpur, MALAYSIA4, 2008, Kuala Lumpur, MALAYSIA
978-1-4244-2867-0/08/$25.00 ©2008 IEEE
R F
M 08
Design of a Spiral Antenna for Wi-Fi Applications
M. F. Abdul Khalid
1, M.A.Haron
1, A. Baharudin
1, and A. A. Sulaiman
2
1Microwave Technology Centre (MTC), Universiti Teknologi MARA, Selangor, Malaysia 2Faculty of Electrical & Electronic Engineering, Universiti Sains Malaysia
Engineering Campus, Pulau Pinang, Malaysia [email protected], [email protected], [email protected], [email protected]
Abstract – The main objective of this project is to
design a spiral antenna at a frequency range between
2.4 to 2.5 GHz. The spiral antenna is fed by a
microstrip line and RT Duroid 5870 is used with
dielectric constant, εr and thickness, tsub of 2.33 and 0.5
mm respectively. For the spiral antenna design and
simulation, the Genesys software is utilised. A
prototype of a circular microstrip antenna is fabricated
and measured. Simulated results like return loss,
VSWR and input impedance are compared with those
obtained from measurements where good agreements
are shown.
Keywords - Spiral antenna, Wi-Fi
1. Introduction
Wi-Fi networks use radio technologies. A person
with a Wi-Fi enabled device such as a PC, cell phone
or PDA can connect to the Internet when in proximity
of an access point. The region covered by one or
several access points is called a hotspot. Hotspots can
range from a single room to many square miles of
overlapping hotspots. Wi-Fi can also be used to create
a mesh network. Both architectures are used in
community networks [1].
Nowadays, Wi-Fi pollution, or an excessive
number of access points in the area, especially on the
same or neighboring channel, can prevent access and
interfere with the use of other access points by others,
caused by overlapping channels in the 802.11g/b
spectrum, as well as with decreased signal-to-noise
ratio (SNR) between access points. This can be a
problem in high-density areas, such as large apartment
complexes or office buildings with many Wi-Fi access
points. Additionally, other devices use the 2.4 GHz
band, microwave ovens, cordless phones, baby
monitors, security cameras, and Bluetooth devices can
cause significant additional interference.
In order to avoid the use of different antennas for
the different services, one multiband or extremely
broadband antenna has to be used. Spiral antennas, that
show frequency independent characteristics at a relatively
small size, are promising candidates for this application.
Additionally planar spiral antennas give the possibility of
conformal integration of the antenna into existing surfaces
such as the car bodywork for reasons of aerodynamics,
stability and aesthetics. Only in recent years the interest in
this type of antenna for communications applications has
increased. The bandwidth of the antenna, which is intended
to cover the radio services range from 800MHz to 2.2GHz.
[2]. In that case, for WiFi application, the bandwidth of the
antenna at the range from 2.4 GHz to 2.5 GHz.
Applications that require low-profile, light weight, easily
manufactured, inexpensive, conformable antennas often
use some form of a microstrip radiator.
2. Design of The Single Arm Spiral Antenna
The spiral antenna which is shown in Fig. 1 consists of
one arm which forms the spiral structure. The arm has
width, w and the separation between the lines is described
by the parameter s. The number of turns of the middle line
is denoted by N and the maximum radius is specified by
rout. The spiral is printed on the dielectric substrate with a
specific thickness tsub and a dielectric constant εr. The input
impedance of the antenna is affected by the line width w,
the distance between the lines s, the dielectric constant εr,
and the substrate thickness tsub.
Fig 1: Geometry of a single arm spiral antenna from the outer
edge.
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2.1 Size The radiation efficiency of the patch antenna
depends largely on the permittivity (εr) of the
dielectric. Ideally, a thick dielectric, low εr and low
insertion loss is preferred for broadband purposes and
increased efficiency. The substrate that used in this
project is 0.5mm thickness and a dielectric constant
value, εr=2.33. Simulation results show suitable
radiation patterns for frequency range between 2.4GHz
and 2.5GHz. The center frequency is at 2.455GHz.
The resonant rectangular patch antenna is on the
order of λ/2 in extent. The length of the element is
reduced by a factor of two if the half-wave patch is
short-circuited to ground at the zero potential planes.
The result is a resonant rectangular patch with length
on the order of λ/4, called a quarter-wave patch.
Certain applications require further size reduction. In
these cases, the shape of the patch is altered to achieve
acceptable performance from rectangular patches with
resonant length less than λ/4.
Fig. 2, 3 and 4 shows the VSWR, return loss
and input impedance graph respectively using three
different microstrip sizes. The length will be constant
and the width is different. The length is constant
because it is the minimum size to ignore the fringing
effect. The size is; (a) 125mm x 115mm, (b) 125mm x
113mm, (c) 125 x 120mm. The best result is the (a)
size.
Fig. 2: VSWR graph for three different antenna sizes.
Table 1: VSWR value compared with different size.
Frequency
GHz Graph (a)
Graph (b)
Graph (c)
2.412 6.792 3.758 4.978
2.455 1.097 12.839 6.550
2.494 6.330 19.418 27.874
The (a) graph shows the best result, VSWR is
1.097 at frequency 2.455GHz. As the width size
decrease, graph (b) show the VSWR is 12.839 at frequency
2.455GHz. Lastly, if the width size is increase, graph (c)
give VSWR value at 2.455GHz is 6.55.
From these entire three graphs, we can see that the
VSWR graph will shift to the left if the width size is
decrease or increase.
Fig. 3 The return loss for three different antenna sizes.
Table 2: Return Loss value with different size.
Frequency
GHz
Graph (a)
Graph (b)
Graph (c)
2.412 -2.576 dB -4.736 dB -3.538 dB
2.455 -26.711 dB -1.356 dB -2.673 dB
2.494 -2.766 dB -0.895 dB -0.623 dB
At frequency 2.455GHz, the return loss for graph
(a) gives the sharpest graph and the value is -26.711 dB.
The graph should be sharp at the center frequency, so that
the minimum return loss will be given for the antenna
design at the center frequency. Graph (a) give the best
result and as the width size is increase or decrease, the
graph will be shift to the left and the graph is not sharp as
the graph (b) compare to graph (a).
Fig. 4: The input impedance for three different antenna sizes.
(a) 125 x 115
(b) 125 x 113
(c) 125 x 120
(a) 125 x 115
(b) 125 x 113
(c) 125 x 120
(a) 125 x 115
(b) 125 x 113
(c) 125 x 120
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Table 3: Input Impedance value compare to different
size.
Frequency
GHz
Graph (a)
Graph (b)
Graph (c)
2.412 196.932 166.077 224.844
2.455 46.363 41.490 31.440
2.494 20.740 48.949 10.578
For the input impedance graph, the value should
be 50 at center frequency because the transmission line
is loaded with a 50ohm resistor at the end. The nearly
value that the simulation can achieve is at 46.353 for
the (a) graph.
As the size is increase or decrease, the input
impedance graph lower the maximum value and the
graph is shift to the right. At the center frequency, the
input impedance value for both graph {graph (b) and
graph (c)} is less than graph (a).
From this analysis, the best result show at graph
(a). The best size for the antenna design is 125mm x
115mm.
2.2 Feeder Network The four most popular feed techniques used are
the microstrip line, coaxial probe (both contacting
schemes), aperture coupling and proximity coupling
(both non-contacting schemes). In this spiral design, it
use microstrip line feed technique.
In this type of feed technique, a conducting
strip is connected directly to the edge of the microstrip
patch as shown in Fig. 5. The conducting strip is
smaller in width as compared to the patch and this
kind of feed arrangement has the advantage that the
feed can be etched on the same substrate to provide a
planar structure.
Fig. 5: Microstrip Line Feed.
The purpose of the inset cut in the patch is to
match the impedance of the feed line to the patch
without the need for any additional matching element.
This is achieved by properly controlling the inset
position. Hence this is an easy feeding scheme, since it
provides ease of fabrication and simplicity in modeling as
well as impedance matching.
However as the thickness of the dielectric
substrate being used, increases, surface waves and spurious
feed radiation also increases, which hampers the bandwidth
of the antenna. The feed radiation also leads to undesired
cross polarized radiation. In simulation, it gives different
result while matching the patch and the feeder line. Fig. 6
shows three different matches to feeder line.
Fig. 6: Three different matching to feeder line. Figure (a)
show the matching feeder that used in the design.
From this three different matching, Fig. 7, 8 and 9
show the result for VSWR, return loss and input
impedance graph respectively.
Fig. 7: Graph VSWR with varying matching with feeder line.
Table 4: VSWR value compared to different feed matching.
Frequency
GHz
Graph (a)
Graph (b)
Graph (c)
2.412 6.792 19.257 30.310
2.455 1.097 6.593 8.694
2.494 6.333 1.443 28.207
(a)
(b)
(c)
Picture (c)
Picture (a) Picture (b)
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From this graph, it shows that there is an
effect for the different matching with the feeder line. If
the patch is nearly align with the y-axis feeder line, as
shown in figure (b), the graph was shifted to the right
and the value at the canter frequency is 6.593.
In figure (c), the patch is over the feeder line
the VSWR graph was shifted to the left and higher
than the reference graph (graph (a)).
Thus, the best graph is the graph (a), for
figure (a). The patch is at the edge of the feeder line.
The VSWR value is 1.097.
Fig 8: Return Loss Graph for different feeder line
matching.
Table 5: Return Loss value compared
to different matching feed line.
Frequency
GHz
Graph (a) Graph (b) Graph (c)
2.412 2.576 dB -0.903 dB -0.573 dB
2.455 -26.711 dB -2.656 dB -2.007 dB
2.494 -2.766 dB -14.834 dB -0.616 dB
Same cases for the return loss graph, Fig 10.
The minimum value for S11 in graph (b) was shifted
to the right and the graph (c) curve is not sharp
compare to the other two graphs. The best graph is still
the graph (a), using figure (a) simulation.
On an edge-fed spiral, the current travels
from the input to the center of the spiral antenna and
gradually emits electromagnetic waves into the air.
Depending on the number of turns and diameter of the
spiral a portion of the bounded electromagnetic waves
reaches the center and then it reflected back towards
the input. The reflected wave travels in the opposite
direction and radiates the opposite circular
polarization.
3. Measurement of Single Arm Spiral Antenna
The single arm spiral antenna was fabricated and its
performance is presented in this section. For the prototype
antenna the width w and spacing s is equal that is 3 mm the
spiral given the outer radius 27mm and consists of 4 turns.
The antenna was fabricated on a rectangular (125mm x
115mm) substrate with εr = 2.33 and a thickness tsub =
0.5mm.
3.1 Measured Return Loss
The return loss of the prototype antenna was
measured from 2.3 – 2.6GHz using a vector analyzer. In
Fig. 12 the simulated and measured result was plotted. The
simulation predicts the band of operation rather accurately.
From the measured graph, compared to the simulated
graph, it is slightly shifted to the right. The minimum
return loss is not at the centre frequency.
The discrepancy between the measured and
simulated results stems from the fact that in the simulations
the antenna substrate and the ground plane are assumed
infinite. The second reason for the observed discrepancy is
the difficulty in connecting a standard 50-Ohm connector
to coplanar feed line of the antenna (see Fig 7). Thus the
feed line is adversely affecting the return loss. Note that
the antenna is not simulated with the connector.
Another reason for the discrepancy can be the gap
width of the coplanar waveguide line at the antenna center.
The return loss is sensitive to small variations of the gap
width as shown in paper. The copper etching cannot
maintain a constant 3mm gap. There is considerable
undercut causing some variations in the characteristic
impedance of the coplanar waveguide.
Fig. 9: Simulated and measured return loss of single arm
spiral antenna.
Table 6: Simulation and measured return loss value.
Frequency
GHz
Simulated
Graph
Measured
Graph
2.412 2.576 dB -5.031 dB
2.455 -26.711 dB -10.024 dB
2.494 -2.766 dB -2.188 dB
simulated
measured
(a)
(b)
(c)
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3.2 Measured VSWR The VSWR measurement and simulation
result was compared in Fig. 10. The measured result is
also slightly shifted to the right. For ideal antenna, the
value for VSWR is equal to 1. Low values of VSWR
indicates the antenna have a small value of reflection
coefficient.
The discrepancies between measurement and
simulation are caused by the assumption of the infinite
substrate and the ground plane in the simulations and
superiors radiations caused by the feed cable and
scattering in the chamber.
A reason for the discrepancy between the
simulated and measured VSWR can be the
measurement setup. A small amount of asymmetry in
the antenna structure, the feed, and the nearby objects
such as the cable feeding the antenna can cause
noticeable errors on the VSWR result.
The other reason for the discrepancy between
measurement and simulation is caused by the
fabrication process. The printer used to print the circuit
layout from the CAD simulation must have high
resolution and high quality printouts. The fabrication
process needs to be handled with care so that the
circuit layouts are precisely constructed on the
microstrip. It is also have to make sure that all part of
the microstrip antenna is grounded.
Fig. 10: Simulated and measured VSWR of single arm
spiral antenna.
Table 7: Simulation and measured VSWR value.
Frequency
GHz
Simulated
Graph
Measured
Graph
2.412 6.792 3.549
2.455 1.097 1.921
2.494 6.333 8.638
6. CONCLUSION
A single arm microstrip antenna topology is
introduced. This spiral antenna is fed from outside edge by
a coplanar waveguide transmission line to achieve a
completely planar antenna that does not require feed
assembly and external matching network. Full-wave
numerical simulations were carried out to optimize the
physical parameters of the antenna. A prototype antenna
above a ground plane was designed, fabricate and its
performance was measured. By optimizing the antenna
gain, the expected results between measure and simulation
are considerably closed. For the future development, the
spiral antenna can vary the arm. Different arm spiral
antenna gives different application and results. Single arm
spiral antenna also can be extended for array single arm
spiral antenna. It can use microstrip antenna fed for the
feeding line. This could be difficult especially during
fabrication process. Another development is the feeding
line, if the microstrip spiral antenna can fed using coaxial
probe. The patch shapes are symmetric and their radiation
is easy to model.
References [1] http://www.Wikipedia.htm/Wi-Fi, 30 July 2007
[2] Johnna Powell and Anantha Chandrakasan, “Spiral Slot Patch
Antenna and Circular Disc Monopole Antenna for 3.1-10.6 GHz Ultra Wideband Communication”, Massachusetts Institute of
Technology, 50 Vassar St. Rm 38-107, Cambridge, MA 02139.
[3] Brad A. Kramer, Chi-Chih Chen and John L. Volakis, “Design and
Performance of an Ultra Wideband Ceramic-Loaded Slot Spiral”,
ElectroScience Laboratory, Electrical and Computer Engineering Dept. The Ohio State University.
[4] Dominikus J. Müller, and Kamal Sarabandi, “Design and Analysis of a 3-Arm Spiral Antenna”, IEEE Transactions On Antennas And
Propagation, vol. 55, No. 2, pp 258-266,
[5] Chang Won Jung, Bedri A. Cetiner And Franco De Flaviis, “A
Single-Arm Circular Spiral Antenna With Inner/Outer Feed
Circuitry For Changing Polarization And Beam Characteristics”, Department Of Electrical And Computer Engineering University Of
California, Irvine, CA, 92697, USA
[6] E. Gschwendtner, W. Wiesbeck, “Low-Cost Spiral Antenna with
Dual-Mode Radiation Pattern for Integrated Radio Services”,
Institut für Höchstfrequenztechnik und Elektronik, University of Karlsruhe, Kaiserstraße 12, 76128 Karlsruhe, Germany
[7] L. Schreider, X. Begaud, M. Soiron, B. Perpere and C. Renard, “Broadband Archimedean spiral antenna above a loaded
electromagnetic band gap substrate”, Special Issue on
Metamaterials EBG
simulated
measured
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